a
FEATURES
High CMV Isolation: 2500 V rms Continuous
3500 V Peak Continuous
Small Size: 1.00" 2.10" 0.350"
Three-Port Isolation: Input, Output, and Power
Low Nonlinearity: 0.012% max
Wide Bandwidth: 20 kHz Full-Power (–3 dB)
Low Gain Drift: 25 ppm/ C max
High CMR: 120 dB (G = 100 V/V)
Isolated Power: 15 V @ 5 mA
Uncommitted Input Amplifier
APPLICATIONS
Multichannel Data Acquisition
High Voltage Instrumentation Amplifier
Current Shunt Measurements
Process Signal Isolation
GENERAL DESCRIPTION
FB
–IN
+IN
I
COM
+V
ISS
–V
ISS
16
17
19
18
14
15
Precision, Wide Bandwidth
3-Port Isolation Amplifier
AD210
FUNCTIONAL BLOCK DIAGRAM
INPUT
T1
MOD
DEMOD
FILTER
1
V
O
OUTPUT
2
T2
INPUT
POWER
SUPPLY
POWER
OSCILLATOR
30
PWR
29
PWR COM
POWER
T3
OUTPUT
POWER
SUPPLY
3
4
O
COM
+V
OSS
–V
OSS
AD210
The AD210 is the latest member of a new generation of low
cost, high performance isolation amplifiers. This three-port,
wide bandwidth isolation amplifier is manufactured with sur-
face-mounted components in an automated assembly process.
The AD210 combines design expertise with state-of-the-art
manufacturing technology to produce an extremely compact
and economical isolator whose performance and abundant user
features far exceed those offered in more expensive devices.
The AD210 provides a complete isolation function with both
signal and power isolation supplied via transformer coupling in-
ternal to the module. The AD210’s functionally complete de-
sign, powered by a single +15 V supply, eliminates the need for
an external DC/DC converter, unlike optically coupled isolation
devices. The true three-port design structure permits the
AD210 to be applied as an input or output isolator, in single or
multichannel applications. The AD210 will maintain its high
performance under sustained common-mode stress.
Providing high accuracy and complete galvanic isolation, the
AD210 interrupts ground loops and leakage paths, and rejects
common-mode voltage and noise that may other vise degrade
measurement accuracy. In addition, the AD210 provides pro-
tection from fault conditions that may cause damage to other
sections of a measurement system.
PRODUCT HIGHLIGHTS
mode voltage isolation between any two ports. Low input
capacitance of 5 pF results in a 120 dB CMR at a gain of 100,
and a low leakage current (2
µA
rms max @ 240 V rms, 60 Hz).
High Accuracy:
With maximum nonlinearity of
±
0.012% (B
Grade), gain drift of
±
25 ppm/°C max and input offset drift of
(± 10
±
30/G)
µV/°C,
the AD210 assures signal integrity while
providing high level isolation.
Wide Bandwidth:
The AD210’s full-power bandwidth of
20 kHz makes it useful for wideband signals. It is also effective
in applications like control loops, where limited bandwidth
could result in instability.
Small Size:
The AD210 provides a complete isolation function
in a small DIP package just 1.00"
×
2.10"
×
0.350". The low
profile DIP package allows application in 0.5" card racks and
assemblies. The pinout is optimized to facilitate board layout
while maintaining isolation spacing between ports.
Three-Port Design:
The AD210’s three-port design structure
allows each port (Input, Output, and Power) to remain inde-
pendent. This three-port design permits the AD210 to be used
as an input or output isolator. It also provides additional system
protection should a fault occur in the power source.
Isolated Power:
±
15 V @ 5 mA is available at the input and
output sections of the isolator. This feature permits the AD210
to excite floating signal conditioners, front-end amplifiers and
remote transducers at the input as well as other circuitry at the
output.
Flexible Input:
An uncommitted operational amplifier is pro-
vided at the input. This amplifier provides buffering and gain as
required and facilitates many alternative input functions as
required by the user.
The AD210 is a full-featured isolator providing numerous user
benefits including:
High Common-Mode Performance:
The AD210 provides
2500 V rms (Continuous) and
±
3500 V peak (Continuous) common-
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
AD210–SPECIFICATIONS
(typical @ +25 C, and V = +15 V unless otherwise noted)
S
Model
GAIN
Range
Error
vs. Temperature(0°C to +70°C)
(–25°C to +85°C)
vs. Supply Voltage
Nonlinearity
1
INPUT VOLTAGE RATINGS
Linear Differential Range
Maximum Safe Differential Input
Max. CMV Input-to-Output
ac, 60 Hz, Continuous
dc, Continuous
Common-Mode Rejection
60 Hz, G = 100 V/V
R
S
≤
500
Ω
Impedance Imbalance
Leakage Current Input-to-Output
@ 240 V rms, 60 Hz
INPUT IMPEDANCE
Differential
Common Mode
AD210AN
1 V/V – 100 V/V
±
2% max
+25 ppm/°C max
±
50 ppm/°C max
±
0.002%/V
±
0.025% max
±
10 V
±
15 V
*
2500 V rms
±
3500 V peak
*
*
120 dB
*
2
µA
rms max
l0
12
Ω
5 GΩ 5 pF
AD210BN
*
±
1% max
*
*
*
±
0.012% max
*
*
*
*
AD210JN
*
*
*
*
*
*
*
*
1500 V rms
±
2000 V peak
*
*
*
*
*
*
*
*
*
*
*
*
*
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
*
*
*
*
AC1059 MATING SOCKET
INPUT BIAS CURRENT
Initial, @ +25°C
30 pA typ (400 pA max) *
10 nA max
*
vs. Temperature (0°C to +70°C)
(–25°C to +85°C) 30 nA max
*
INPUT DIFFERENCE CURRENT
Initial, @ +25°C
vs. Temperature(0°C to + 70°C)
(–25°C to +85°C)
INPUT NOISE
Voltage (l kHz)
(10 Hz to 10 kHz)
Current (1 kHz)
5 pA typ (200 pA max)
2 nA max
10 nA max
18 nV/√Hz
4
µV
rms
0.01 pA/√Hz
*
*
*
*
*
*
FREQUENCY RESPONSE
Bandwidth (–3 dB)
*
G = 1 V/V
20 kHz
G = 100 V/V
15 kHz
Settling Time (± 10 mV, 20 V Step) *
G = 1 V/V
150
µs
G = 100 V/V
500
µs
Slew Rate (G = 1 V/V)
1 V/µs
OFFSET VOLTAGE (RTI)
Initial, @ +25°C
vs. Temperature (0°C to +70°C)
(–25°C to +85°C)
RATED OUTPUT
3
Voltage, 2 kΩ Load
Impedance
Ripple (Bandwidth = 100 kHz)
ISOLATED POWER OUTPUTS
4
Voltage, No Load
Accuracy
Current
Regulation, No Load to Full Load
Ripple
POWER SUPPLY
Voltage, Rated Performance
Voltage, Operating
Current, Quiescent
Current, Full Load – Full Signal
TEMPERATURE RANGE
Rated Performance
Operating
Storage
PACKAGE DIMENSIONS
Inches
Millimeters
2
*
*
*
*
*
(± 5
±15/G)
mV max
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
*
AD210 PIN DESIGNATIONS
Pin
1
2
3
4
14
15
16
17
18
19
29
30
Designation
V
O
O
COM
+V
OSS
–V
OSS
+V
ISS
–V
ISS
FB
–IN
I
COM
+IN
Pwr Com
Pwr
Function
Output
Output Common
+Isolated Power @ Output
–Isolated Power @ Output
+Isolated Power @ Input
–Isolated Power @ Input
Input Feedback
–Input
Input Common
+Input
Power Common
Power Input
±
15
±
45/G) mV max
(± 10
±
30/G)
µV/°C
(± 10
±
50/G)
µV/°C
±
10 V min
1
Ω
max
10 mV p-p max
±
15 V
±
10%
±
5 mA
See Text
See Text
+15 V dc
±
5%
+15 V dc
±
10%
50 mA
80 mA
–25°C to +85°C
–40°C to +85°C
–40°C to +85°C
1.00
×
2.10
×
0.350
25.4
×
53.3
×
8.9
WARNING!
ESD SENSITIVE DEVICE
NOTES
*Specifications same as AD210AN.
1
Nonlinearity is specified as a % deviation from a best straight line..
2
RTI – Referred to Input.
3
A reduced signal swing is recommended when both
±
V
ISS
and
±
V
OSS
supplies are fully
loaded, due to supply voltage reduction.
4
See text for detailed information.
_
Specifications subject to change without notice.
CAUTION
ESD (electrostatic discharge) sensitive device. Elec-
trostatic charges as high as 4000 V readily accumu-
late on the human body and test equipment and can
discharge without detection. Although the AD210
features proprietary ESD protection circuitry, per-
manent damage may occur on devices subjected to
high energy electrostatic discharges. Therefore,
proper ESD precautions are recommended to avoid
performance degradation or loss of functionality.
–2–
REV. A
AD210
INSIDE THE AD210
The AD210 basic block diagram is illustrated in Figure 1.
A +15 V supply is connected to the power port, and
±
15 V isolated power is supplied to both the input and
output ports via a 50 kHz carrier frequency. The uncom-
mitted input amplifier can be used to supply gain or buff-
ering of input signals to the AD210. The fullwave
modulator translates the signal to the carrier frequency for
application to transformer T1. The synchronous demodu-
lator in the output port reconstructs the input signal. A
20 kHz, three-pole filter is employed to minimize output
noise and ripple. Finally, an output buffer provides a low
impedance output capable of driving a 2 kΩ load.
FB
–IN
+IN
I
COM
+V
ISS
–V
ISS
16
17
19
18
14
15
T2
INPUT
POWER
SUPPLY
POWER
OSCILLATOR
30
PWR
29
PWR COM
POWER
T3
OUTPUT
POWER
SUPPLY
3
4
+V
OSS
INPUT
T1
MOD
DEMOD
FILTER
1
V
O
OUTPUT
R
F
16
17
V
SIG
R
G
18
19
1
V
OUT
R
= V
SIG
1+
F
R
G
(
)
AD210
2
14
15
+V
ISS
–V
ISS
30
+15V
29
+V
OSS
–V
OSS
3
4
Figure 3. Input Configuration for G > 1
Figure 4 shows how to accommodate current inputs or sum cur-
rents or voltages. This circuit configuration can also be used for
signals greater than
±
10 V. For example, a
±
100 V input span
can be handled with R
F
= 20 kΩ and R
S1
= 200 kΩ.
I
S
R
F
16
17
1
V
OUT
2
+V
ISS
–V
ISS
30
V
S1
+15V
29
2
O
COM
–V
OSS
R
S2
V
S2
R
S1
V
S1
19
AD210
AD210
18
14
15
Figure 1. AD210 Block Diagram
+V
OSS
–V
OSS
3
4
USING THE AD210
The AD210 is very simple to apply in a wide range of ap-
plications. Powered by a single +15 V power supply, the
AD210 will provide outstanding performance when used
as an input or output isolator, in single and multichannel
configurations.
Input Configurations:
The basic unity gain configura-
tion for signals up to
±
10 V is shown in Figure 2. Addi-
tional input amplifier variations are shown in the following
figures. For smaller signal levels Figure 3 shows how to
obtain gain while maintaining a very high input impedance.
16
17
V
SIG
±10V
19
1
V
OUT
V
OUT
(±10V)
2
+V
ISS
–V
ISS
30
+15V
29
V
OUT
= –R
F
(
R
S1
+ R
S2
S2
V
+ I
S
+ ...
)
Figure 4. Summing or Current Input Configuration
Adjustments
When gain and offset adjustments are required, the actual cir-
cuit adjustment components will depend on the choice of input
configuration and whether the adjustments are to be made at
the isolator’s input or output. Adjustments on the output side
might be used when potentiometers on the input side would
represent a hazard due to the presence of high common-mode
voltage during adjustment. Offset adjustments are best done at
the input side, as it is better to null the offset ahead of the gain.
Figure 5 shows the input adjustment circuit for use when the in-
put amplifier is configured in the noninverting mode. This offset
adjustment circuit injects a small voltage in series with the
GAIN
47.5kΩ
16
5kΩ
17
19
V
SIG
R
G
HI
LO
200Ω
14
100kΩ
50kΩ
OFFSET
15
–V
ISS
30
+15V
29
–V
OSS
4
+V
ISS
+V
OSS
3
18
1
V
OUT
AD210
18
14
15
+V
OSS
–V
OSS
3
4
Figure 2. Basic Unity Gain Configuration
AD210
2
The high input impedance of the circuits in Figures 2 and
3 can be maintained in an inverting application. Since the
AD210 is a three-port isolator, either the input leads or
the output leads may be interchanged to create the signal
inversion.
Figure 5. Adjustments for Noninverting Input
REV. A
–3–
AD210
low side of the signal source. This will not work if the source has
another current path to input common or if current flows in the
signal source LO lead. To minimize CMR degradation, keep the
resistor in series with the input LO below a few hundred ohms.
Figure 5 also shows the preferred gain adjustment circuit. The
circuit shows R
F
of 50 kΩ, and will work for gains of ten or
greater. The adjustment becomes less effective at lower gains
(its effect is halved at G = 2) so that the pot will have to be a
larger fraction of the total R
F
at low gain. At G = 1 (follower)
the gain cannot be adjusted downward without compromising
input impedance; it is better to adjust gain at the signal source
or after the output.
Figure 6 shows the input adjustment circuit for use when the
input amplifier is configured in the inverting mode. The offset
adjustment nulls the voltage at the summing node. This is pref-
erable to current injection because it is less affected by subse-
quent gain adjustment. Gain adjustment is made in the feedback
and will work for gains from 1 V/V to 100 V/V.
GAIN
47.5kΩ
5kΩ
R
S
V
SIG
50kΩ
14
100kΩ
15
OFFSET
–V
ISS
30
+15V
29
–V
OSS
4
+V
ISS
+V
OSS
3
200Ω
18
16
17
19
1
V
OUT
1
R
G
R
F
R
G
R
F
2
CHANNEL INPUTS
3
R
G
R
F
CHANNEL OUTPUTS
1
2
3
0.1"
GRID
POWER
AD210
2
Figure 8. PCB Layout for Multichannel Applications with
Gain
Synchronization:
The AD210 is insensitive to the clock of an
adjacent unit, eliminating the need to synchronize the clocks.
However, in rare instances channel to channel pick-up may
occur if input signal wires are bundled together. If this happens,
shielded input cables are recommended.
PERFORMANCE CHARACTERISTICS
Figure 6. Adjustments for Inverting Input
Figure 7 shows how offset adjustments can be made at the out-
put, by offsetting the floating output port. In this circuit,
±
15 V
would be supplied by a separate source. The AD210’s output
amplifier is fixed at unity, therefore, output gain must be made
in a subsequent stage.
16
17
19
1
Common-Mode Rejection:
Figure 9 shows the common-
mode rejection of the AD210 versus frequency, gain and input
source resistance. For maximum common-mode rejection of
unwanted signals, keep the input source resistance low and care-
fully lay out the input, avoiding excessive stray capacitance at
the input terminals.
180
G = 100
R
L
O
=0
Ω
160
V
OUT
G=1
140
AD210
18
+V
ISS
–V
ISS
30
+15V
29
2
200Ω
14
15
+V
OSS
–V
OSS
3
4
50kΩ
R
L
CMR – dB
120
100
R
L
O
=5
00
Ω
O
=0
Ω
0.1µF
100k
OFFSET
+15V
–15V
R
L
R
L
O
=1
0k
Ω
80
60
O
=1
0k
Ω
Figure 7. Output-Side Offset Adjustment
40
10
20
50 60 100
200
500
1k
2k
5k
10k
FREQUENCY – Hz
PCB Layout for Multichannel Applications:
The unique
pinout positioning minimizes board space constraints for multi-
channel applications. Figure 8 shows the recommended printed
circuit board layout for a noninverting input configuration with
gain.
Figure 9. Common-Mode Rejection vs. Frequency
–4–
REV. A
AD210
Phase Shift:
Figure 10 illustrates the AD210’s low phase shift
and gain versus frequency. The AD210’s phase shift and wide
bandwidth performance make it well suited for applications like
power monitors and controls systems.
ERROR – %
+0.04
+0.03
+0.02
+0.01
0
–0.01
–0.02
–0.03
–0.04
–10
–8
–6
–4
–2
0
+2
+4
+6
+8
+8
+6
+4
ERROR – mV
60
0
–20
–40
–60
–80
–100
–120
–140
100k
PHASE SHIFT – Degrees
+2
0
–2
–4
–6
–8
+10
OUTPUT VOLTAGE SWING – Volts
40
φG
= 1
20
GAIN – dB
φG
= 100
0
–20
–40
–60
Figure 12. Gain Nonlinearity Error vs. Output
100
90
ERROR – ppm of Signal Swing
–80
10
100
1k
FREQUENCY – Hz
10k
0.01
0.009
ERROR – % of Signal Swing
Figure 10. Phase Shift and Gain vs. Frequency
80
70
60
50
40
30
20
10
0
0
2
4
6
8
10
12
14
16
18
20
TOTAL SIGNAL SWING – Volts
0.008
0.007
0.006
0.005
0.004
0.003
0.002
0.001
0.000
Input Noise vs. Frequency:
Voltage noise referred to the input
is dependent on gain and signal bandwidth. Figure 11 illustrates
the typical input noise in nV/√Hz of the AD210 for a frequency
range from 10 to 10 kHz.
60
50
NOISE – nV/
√
Hz
40
30
Figure 13. Gain Nonlinearity vs. Output Swing
20
10
Gain vs. Temperature:
Figure 14 illustrates the AD210’s
gain vs. temperature performance. The gain versus temperature
performance illustrated is for an AD210 configured as a unity
gain amplifier.
400
0
10
100
FREQUENCY – Hz
GAIN ERROR – ppm of Span
1k
10k
200
0
–200
–400
–600
–800
–1000
–1200
–1400
–1600
–25
0
+25
+50
+70
+85
TEMPERATURE –
°C
G=1
Figure 11. Input Noise vs. Frequency
Gain Nonlinearity vs. Output:
Gain nonlinearity is defined as the
deviation of the output voltage from the best straight line, and is
specified as % peak-to-peak of output span. The AD210B provides
guaranteed maximum nonlinearity of
±
0.012% with an output span of
±
10 V. The AD210’s nonlinearity performance is shown in Figure 12.
Gain Nonlinearity vs. Output Swing:
The gain nonlinearity
of the AD210 varies as a function of total signal swing. When
the output swing is less than 20 volts, the gain nonlinearity as a
fraction of signal swing improves. The shape of the nonlinearity
remains constant. Figure 13 shows the gain nonlinearity of the
AD210 as a function of total signal swing.
Figure 14. Gain vs. Temperature
REV. A
–5–
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