TECHNICAL DATA
TELEPHONE SPEECH NETWORK
WITH DIALER INTERFACE
FEATURES
•
Low DC line voltage; operates down to 1.6V (excluding polarity
guard)
•
Voltage regulator with adjustable static resistance
•
Provides a supply for external circuits
•
Symmetrical high-impedance inputs (64 kΩ) for dynamic,
magnetic or piezo-electric microphones
•
Asymmetrical high-impedance input (32 kΩ) for electrets
microphones
•
DTMF signal input with confidence tone
•
Mute input for pulse or DTMF dialing
- ILA1062: active HIGH (MUTE)
- ILA1062A: active LOW (MUTE)
•
Receiving amplifier for dynamic, magnetic or piezo-electric
earpieces
•
Large gain setting range on microphone and earpiece
amplifiers
•
Line loss compensation (line current dependent) for
microphone and earpiece amplifiers
•
Gain control curve adaptable to exchange supply
•
DC line voltage adjustment facility
ILA1062/1062A
ILA1062N/AN Plastic
ILA1062D/AD SOIC
PIN CONNECTION
ORDERING INFORMATION
Device
ILA1062N
ILA1062AN
ILA1062D
ILA1062AD
ILA1062DT
ILA1062ADT
Operating
Temperature Range
Package
DIP8
DIP8
SOP8
SOP8
SOP8
SOP8
Packing
Tube
Tube
Tube
Tube
Tape & Reel
Tape & Reel
T
A
= -25° to 75° C
DESCRIPTION
The ILA1062 and ILA1062A are integrated circuits that perform all speech and line interface functions
required in fully electronic telephone sets. They perform electronic switching between dialing and speech.
The ICs operates at line voltage down to 1.6 V DC (with reduced performance) to facilitate the use of more
telephone sets connected in parallel.
All statements and values refer to all versions unless otherwise specified. The ILA1062 (ILA1062A) is
packaged in a standard 16-pin plastic DIP and special plastic DIP with internal heatsink is also available.
2011, March, ver.01
ILA1062/1062A
QUICK REFERENCE DATA
Characteristic
Line Voltage
Operating Line Current
Normal Operation
with Reduced Performance
Internal Supply Current
Supply Voltage for Peripherals
I
CC
V
CC
V
CC
= 2.8V
I
line
= 15mA
I
p
= 1.2mA
I
p
= 0mA
Symbol
V
LN
I
line
11
1
0.9
2.2
2.2
44
20
∆G
V
V
exch
R
exch
36
0.4
5.8
60
1
2.7
3.4
52
31
dB
dB
dB
V
kΩ
Test Condition
I
line
= 15mA
Min
3.55
Typ
4.0
2.0
140
11
1.35
Max
4.25
Unit
V
V
dc
mA
mA
mA
V
Voltage Gain
microphone amplifier
receiving amplifier
Line loss compensation
Gain Control
Exchange Supply Voltage
Exchange Feeding bridge
Resistance
G
V
BLOCK DIAGRAM
V
CC
13
10
-
LN
1
5
IR
GAR
ILA1062A
BT1062A
+
4
QR
MIC+
MIC-
7
6
+
2
-
-
GAS1
+
DTMF
(1)
11
+
3
GAS2
dB
-
12
MUTE
SUPPLY AND
REFERENCE
CONTROL
CURRENT
LOW VOLTAGE
CIRCUIT
CURRENT
REFERENCE
9
V
EE
14
REG
15
AGC
8
STAB
16
SLPE
(1) Pin 12 is active HIGH (MUTE) for ILA1062.
Fig.1 Block diagram of ILA1062A
2011, March, ver.01
ILA1062/1062A
FUNCTIONAL DESCRIPTION
Supplies V
CC
, LN, SLPE, REG and STAB
Power for the IC and its peripheral circuits is usually
obtained from the telephone line. The supply voltage is
delivered from the line via a dropping resistor and
regulated by the IC. The supply voltage V
CC
may also
be used to supply external circuits e.g. dialing and
control circuits.
Decoupling of the supply voltage is performed by a
capacitor between V
CC
and V
EE
. The internal voltage
regulator is decoupled by a capacitor between REG and
V
EE.
The DC current flowing into the set is determined by
the exchange supply voltage V
exch
, the feeding bridge
resistance R
exch
and the DC resistance of the telephone
line R
line
.
The circuit has internal current stabilizer operating at a
level determined by a 3.6 kΩ resistor connected
between STAB and V
EE
(see Fig.6). When the line
current (I
line
) is more than 0.5mA greater than the sum
of the IC supply current (I
CC
) and the current drawn by
the peripheral circuitry connected to V
CC
(I
p
) the excess
current is shunted to V
EE
via LN.
The regulated voltage on the line terminal (V
LN
) can be
calculated as:
V
LN
= V
ref
+ I
SLPE
x R9
V
LN
= V
ref
+ {(I
line
- I
CC
- 0.5 x 10
-3
A) - I
p
} x R9
V
ref
is an internally generated temperature compensated
reference voltage of 3.7V and R9 is an external resistor
connected between SLPE and V
EE.
In normal use the value of R9 would be 20Ω.
Changing the value of R9 will also affect microphone
gain, DTMF gain, gain control characteristics, sidetone
level, maximum output swing on LN and the DC
characteristics (especially at the lower voltages).
Under normal conditions, when I
SLPE
>>I
CC
+ 0.5mA +
I
p
, the static behaviour of the circuit is that of a 3.7V
regulator diode with an internal resistance equal to that
of R9. In the audio frequency range the dynamic
impedance is largely determined by R1. Fig.2 show the
equivalent impedance of the circuit.
At line currents below 9mA the internal reference
voltage is automatically adjusted to a lower value
(typically 1.6V at 1mA). This means that more sets can
be operated in parallel with DC line voltage (excluding
the polarity guard) down to an absolute minimum
voltage of 1.6V. At line currents below 9mA the circuit
has limited sending and receiving levels. The internal
reference voltage can be adjusted by means of an
external resistor (R
VA
). This resistor when connected
between LN and REG will decrease the internal
reference voltage and when connected between REG
and SLPE will increase the internal reference voltage.
Microphone inputs MIC+ and MIC- and gain pins
GAS1 and GAS2
The circuit has symmetrical microphone inputs. Its
input impedance is 64 kΩ (2 x 32kΩ) and its voltage
gain is typically 52 dB (when R7 = 68kΩ; see Fig.6).
Dynamic, magnetic, piezo-electric or electret (with
built-in FET source followers) can be used.
The gain of the microphone amplifier can be adjusted
between 44 dB and 52 dB to suit the sensitivity of the
transducer in use. The gain is proportional to the value
of R7 which is connected between GAS1 and GAS2.
Stability is ensured by two external capacitors, C6
connected between GAS1 and SLPE and C8 connected
between GAS1 and VEE. The value of C6 is 100pF but
this may be increased to obtain a first-order low-pass
filter. The value of C8 is 10 times the value of C6. The
cut-off frequency corresponds to the time constant R7 x
C6.
Input MUTE (ILA1062A)
When MUTE is LOW or open-circuit, the DTMF input
is enable and the microphone and receiving amplifier
inputs are inhibited. The reverse is true when MUTE is
HIGH.
MUTE switching causes only negligible clicking on the
line and earpiece output. If the number of parallel sets
in use causes a drop in line current to below 6 mA the
DTMF amplifier becomes active independent to the DC
level applied to the MUTE input.
Fig.2 Equivalent impedance circuit
2011, March, ver.01
ILA1062/1062A
Dual-tone multi-frequency input DTMF
When the DTMF input is enable dialing tones may be
sent on to the line. The voltage gain from DTMF to LN
is typically 25.5 dB (when R7=68kΩ) and varies with
R7 in the same way as the microphone gain. The
signaling tones can be heard in the earpiece at a low
level (confidence tone).
Receiving amplifier IR, QR and GAR
The receiving amplifier has one input (IR) and a non-
inverting output (QR). The IR to QR gain is typically
31dB (when R4 = 100kΩ). It can be adjusted between
20 and 31dB to match the sensitivity of the transducer
in use. The gain is set with the value of R4 which is
connected between GAR and QR. The overall receive
gain, between LN and QR, is calculated by subtracting
the anti-sidetone network attenuation (32dB) from the
amplifier gain. Two external capacitors, C4 and C7,
ensure stability. C4 is normally 100pF and C7 is 10
times the value of C4. The value of C4 may be
increased to obtain a first-order low-pass filter. The
cut-off frequency will depend on the time constant R4 x
C4.
The output voltage of the receiving amplifier is
specified for continuous-wave drive. The maximum
output voltage will be higher under speech conditions
where the peak to RMS ratio is higher.
Automatic gain control input AGC
Automatic line loss compensation is achieved by
connecting a resistor (R6) between AGC and V
EE
.
The automatic gain control varies the gain of the
microphone amplifier and the receiving amplifier in
accordance with the DC line current. The control range
is 5.8 dB which corresponds to a line length of 5 km for
a 0.5mm diameter twisted-pair copper cable with a DC
resistance of 176 dB/km and average attenuation of
1.2dB/km. Resistor R6 should be chosen in accordance
with the exchange supply voltage and its feeding bridge
resistance. The ratio of start and stop currents of the
AGC curve is independent of the value of R6. If no
automatic line-loss compensation is required the AGC
pin may be left open-circuit. The amplifiers, in this
condition, will give their maximum specified gain.
Sidetone suppression
The anti-sidetone network, R1//Z
line
, R2, R3, R8, R9
and Z
bal
suppresses the transmitted signal in the
earpiece. Maximum compensation is obtained when the
following conditions are fulfilled:
R 8 x Z
bal
R9 x R2 = R1 x
R 3
+
R 8
+
Z
bal
Z
bal
Z
bal
+
R 8
(1)
=
Z
line
Z
line
+
R 1
(2)
If fixed values are chosen for R1, R2, R3 and R9, then
condition (1) will always be fulfilled when
To obtain optimum sidetone suppression, condition (2)
has to be fulfilled which results in:
Z
bal
=
R8
R1
x Z
line
= k x Z
line
R8
R1
Where k is scale factor; k =
The scale factor k, dependent on the value of R8, is
chosen to meet the following criteria:
- compatibility with a standard capacitor from the E6 or
E12 range for Z
bal
-
|Z
bal
//R8|<<R8 fulfilling condition (a) and thus
ensuring correct
anti-sidetone bridge operation
-
|Z
bal
+ R8|>>R9 to avoid influencing the transmit gain.
In practise Z
line
varies considerably with the line type
and length. The value chosen for Z
bal
should therefore
be for an average line thus giving optimum setting for
short or long lines.
2011, March, ver.01
ILA1062/1062A
ABSOLUTE MAXIMUM RATING
Characteristic
Positive Continuous Line Voltage
Repetitive Line Voltage During
Switch-on or Line Interruption
Repetitive Peak Line Voltage for a
1ms Pulse per 5s
Line Current
Input Voltage on all other Pins
Total Power Standard DIP
Dissipation
DIP with heatsink
Operating Ambient Temperature
Storage Temperature
Junction Temperature
Symbol
V
LN
V
LN(R)
V
LN(RM)
I
line
V
I
P
tot
T
A
T
stg
T
j
R9 = 20Ω; R10 = 13Ω;
see Fig.6
R9 = 20Ω; note 1
-0.7
R9 = 20Ω; note 2
-25
-40
Test Condition
Min
Typ
Max
12
13.2
28
140
V
CC
+0.7
0.58
0.67
+75
+125
+125
Unit
V
V
V
mA
V
W
o
o
C
C
o
C
Notes
1. Mostly dependent on the maximum required T
A
and on the voltage between LN and SLPE.
o
2. Calculated for the maximum ambient temperature specified and a maximum junction temperature of 125 C.
o
o
(Thermal Resistance R
JA
= 85 C/W for standard DIP and R
JA
= 75 C/W for special DIP with heatsink).
3. Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device.
These are stress ratings only and functional operation of the device at these or any other conditions beyond those
indicated under “recommended operating conditions” is not implied.
Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
150
I
LN
(mA)
130
150
I
LN
(mA)
130
110
(1)
90
(2)
110
(1)
(2)
(3)
90
70
(3)
(4)
70
(4)
50
50
30
2
4
6
8
10
12
V
LN
- V
SLPE
(V)
30
2
4
6
8
10
12
V
LN
- V
SLPE
(V)
(1)
(2)
(3)
(4)
T
A
= 45
o
C; P
tot
= 0.94 W
T
A
= 55
o
C; P
tot
= 0.82 W
T
A
= 65
o
C; P
tot
= 0.71 W
T
A
= 75
o
C; P
tot
= 0.58 W
Fig.3a Safe operating area
(Standard DIP)
(1)
(2)
(3)
(4)
T
A
= 45
o
C; P
tot
= 1.07 W
T
A
= 55
o
C; P
tot
= 0.93 W
T
A
= 65
o
C; P
tot
= 0.80 W
T
A
= 75
o
C; P
tot
= 0.67 W
Fig.3b Safe operating area
(DIP with HS)
2011, March, ver.01
无线连接
京公网安备 11010802033920号
Copyright © 2005-2026 EEWORLD.com.cn, Inc. All rights reserved
电子工程世界
