®
HS-1135RH
Data Sheet
April 6, 2009
FN4099.3
Radiation Hardened, High Speed, Low
Power Current Feedback Amplifier with
Programmable Output Limiting
The HS-1135RH is a radiation hardened, high speed, low
power current feedback amplifier built with Intersil’s
proprietary complementary bipolar UHF-1 (DI bonded wafer)
process. They are QML approved and processed in full
compliance with MIL-PRF-38535. This amplifier features
user programmable output limiting, via the V
H
and V
L
pins.
The HS-1135RH is the ideal choice for high speed, low
power applications requiring output limiting (e.g., flash A/D
drivers), especially those requiring fast overdrive recovery
times. The limiting function allows the designer to set the
maximum and minimum output levels to protect downstream
stages from damage or input saturation. The
sub-nanosecond overdrive recovery time ensures a quick
return to linear operation following an overdrive condition.
Component and composite video systems also benefit from
this op amp’s performance, as indicated by the gain flatness,
and differential gain and phase specifications.
Specifications for Rad Hard QML devices are controlled
by the Defense Supply Center in Columbus (DSCC). The
SMD numbers listed here must be used when ordering.
Detailed Electrical Specifications for these devices are
contained in SMD 5962-96767. A “hot-link” is provided
on our website for downloading.
Features
• Electrically Screened to SMD # 5962-96767
• QML Qualified per MIL-PRF-38535 Requirements
• User Programmable Output Voltage Limiting
• Fast Overdrive Recovery . . . . . . . . . . . . . . . . . <1ns (Typ)
• Low Supply Current . . . . . . . . . . . . . . . . . . . . 6.9mA (Typ)
• Wide -3dB Bandwidth. . . . . . . . . . . . . . . . . .360MHz (Typ)
• High Slew Rate . . . . . . . . . . . . . . . . . . . . .1200V/µs (Typ)
• High Input Impedance . . . . . . . . . . . . . . . . . . . 2MΩ (Typ)
• Excellent Gain Flatness (to 50MHz). . . . . .
±0.07dB
(Typ)
• Total Gamma Dose . . . . . . . . . . . . . . . . . . . 300kRAD(Si)
• Latch Up. . . . . . . . . . . . . . . . . . . . . None (DI Technology)
Applications
• Flash A/D Driver
• Video Switching and Routing
• Pulse and Video Amplifiers
• Wideband Amplifiers
• RF/IF Signal Processing
• Imaging Systems
Pinouts
HS-1135RH
GDIP1-T8 (CERDIP)
OR CDIP2-TI (SBDIP)
TOP VIEW
NC
-IN
+IN
V-
1
2
3
4
8
V
H
V+
OUT
V
L
HS-1135RH
CDFP3-F14 (FLATPACK)
TOP VIEW
NC
NC
-IN
+IN
NC
NC
V-
1
2
3
4
5
6
7
14
13
12
11
10
9
8
NC
V
H
V+
OUT
V
L
NC
NC
-
+
7
6
5
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774
|
Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 1999, 2009. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
HS-1135RH
Ordering Information
ORDERING NUMBER
(Note)
5962F9676701VPC
5962F9676701VXC
HS7B-1135RH/PROTO
HS9-1135RH/PROTO
INTERNAL
MKT. NUMBER
HS7B-1135RH-Q
HS9-1135RH-Q
HS7B-1135RH/PROTO
HS9-1135RH/PROTO
PART MARKING
Q5962F96 76701VPC
Q5962F96 76701VXC
HS7B- 1135RH /PROTO
HS9- 1135RH /PROTO
TEMP. RANGE
(°C)
-55 to +125
-55 to +125
-55 to +125
-55 to +125
PACKAGE
8 Ld SBDIP
8 Ld Flatpack
8 Ld SBDIP
8 Ld Flatpack
D8.3
K14.A
D8.3
K14.A
PKG DWG #
NOTE: These Intersil Pb-free Hermetic packaged products employ 100% Au plate - e4 termination finish, which is RoHS compliant and compatible
with both SnPb and Pb-free soldering operations.
2
FN4099.3
April 6, 2009
HS-1135RH
Clamp Operation
General
The HS-1135RH features user programmable output clamps
to limit output voltage excursions. Clamping action is obtained
by applying voltages to the V
H
and V
L
terminals (pins 8 and 5)
of the amplifier. V
H
sets the upper output limit, while V
L
sets
the lower clamp level. If the amplifier tries to drive the output
above V
H
, or below V
L
, the clamp circuitry limits the output
voltage at V
H
or V
L
(± the clamp accuracy), respectively. The
low input bias currents of the clamp pins allow them to be
driven by simple resistive divider circuits, or active elements
such as amplifiers or DACs.
the clamp inputs floating. A similar description applies to the
symmetrical low clamp circuitry controlled by V
L
.
When the output is clamped, the negative input continues to
source a slewing current (I
CLAMP
) in an attempt to force the
output to the quiescent voltage defined by the input. Q
P5
must
sink this current while clamping, because the -IN current is
always mirrored onto the high impedance node. The clamping
current is calculated as (V
-IN
- V
OUT
)/R
F
. As an example, a
unity gain circuit with V
IN
= 2V, V
H
= 1V, and R
F
= 510Ω
would have I
CLAMP
= (2-1)/510Ω = 1.96mA. Note that I
CC
will
increase by I
CLAMP
when the output is clamp limited.
Clamp Accuracy
The clamped output voltage will not be exactly equal to the
voltage applied to V
H
or V
L
. Offset errors, mostly due to V
BE
mismatches, necessitate a clamp accuracy parameter which is
found in the device specifications. Clamp accuracy is a function
of the clamping conditions. Referring again to Figure 1, it can
be seen that one component of clamp accuracy is the V
BE
mismatch between the Q
X6
transistors, and the Q
X5
transistors.
If the transistors always ran at the same current level, there
would be no V
BE
mismatch, and no contribution to the
inaccuracy. The Q
X6
transistors are biased at a constant
current, but as described earlier, the current through Q
X5
is
equivalent to I
CLAMP
. V
BE
increases as I
CLAMP
increases,
causing the clamped output voltage to increase as well. I
CLAMP
is a function of the overdrive level (V
-IN
-V
OUTCLAMPED
) and
R
F
, so clamp accuracy degrades as the overdrive increases, or
as R
F
decreases. As an example, the specified accuracy of
±60mV
for a 2X overdrive with R
F
= 510Ω degrades to
±220mV
for R
F
= 240Ω at the same overdrive, or to
±250mV
for a 3X
overdrive with R
F
= 510Ω.
Consideration must also be given to the fact that the clamp
voltages have an effect on amplifier linearity.
Clamp Circuitry
Figure 1 shows a simplified schematic of the HS-1135RH
input stage, and the high clamp (V
H
) circuitry. As with all
current feedback amplifiers, there is a unity gain buffer
(Q
X1
- Q
X2
) between the positive and negative inputs. This
buffer forces -IN to track +IN, and sets up a slewing current
of (V
-IN
- V
OUT
)/R
F
. This current is mirrored onto the high
impedance node (Z) by Q
X3
-Q
X4
, where it is converted to a
voltage and fed to the output via another unity gain buffer. If
no clamping is utilized, the high impedance node may swing
within the limits defined by Q
P4
and Q
N4
. Note that when the
output reaches it’s quiescent value, the current flowing
through -IN is reduced to only that small current (-I
BIAS
)
required to keep the output at the final voltage.
V+
Q
P3
Q
P4
50k
(30k
FOR V
L
)
Z
+1
V
H
Q
N5
Q
P2
Q
P5
Q
N6
Q
P6
Q
N4
200Ω
Q
N2
Q
P1
+IN
V-
V+
Q
N1
I
CLAMP
R
1
Clamp Range
Unlike some competitor devices, both V
H
and V
L
have usable
ranges that cross 0V. While V
H
must be more positive than V
L
,
both may be positive or negative, within the range restrictions
indicated in the specifications. For example, the HS-1135RH
could be limited to ECL output levels by setting V
H
= -0.8V and
V
L
= -1.8V. V
H
and V
L
may be connected to the same voltage
(GND for instance) but the result won’t be in a DC output
voltage from an AC input signal. A 150 - 200mV AC signal will
still be present at the output.
Q
N3
V-
-IN
R
F
(EXTERNAL)
V
OUT
FIGURE 1. HS-1135RH SIMPLIFIED V
H
CLAMP CIRCUITRY
Recovery from Overdrive
The output voltage remains at the clamp level as long as the
overdrive condition remains. When the input voltage drops
below the overdrive level (V
CLAMP
/A
VCL
) the amplifier will
return to linear operation. A time delay, known as the
Overdrive Recovery Time, is required for this resumption of
linear operation. The plots of “Unclamped Performance” and
“Clamped Performance” highlight the HS-1135RH’s sub
nanosecond recovery time. The difference between the
unclamped and clamped propagation delays is the overdrive
FN4099.3
April 6, 2009
Tracing the path from V
H
to Z illustrates the effect of the
clamp voltage on the high impedance node. V
H
decreases
by 2V
BE
(QN6 and QP6) to set up the base voltage on QP5.
QP5 begins to conduct whenever the high impedance node
reaches a voltage equal to QP5’s base + 2V
BE
(QP5 and
QN5). Thus, QP5 clamps node Z whenever Z reaches V
H
.
R1 provides a pull-up network to ensure functionality with
3
HS-1135RH
recovery time. The appropriate propagation delays are 4.0ns
for the unclamped pulse, and 4.8ns for the clamped (2X
overdrive) pulse yielding an overdrive recovery time of
800ps. The measurement uses the 90% point of the output
transition to ensure that linear operation has resumed. Note:
The propagation delay illustrated is dominated by the
fixturing. The delta shown is accurate, but the true
HS-1135RH propagation delay is 500ps.
The layout and schematic of the board are shown in the
following:
V
H
1
+IN
V
L
OUT
V+
V-
GND
Use of Die in Hybrid Applications
This amplifier is designed with compensation to negate the
package parasitics that typically lead to instabilities. As a
result, the use of die in hybrid applications results in
overcompensated performance due to lower parasitic
capacitances. Reducing R
F
below the recommended values
for packaged units will solve the problem. For A
V
= +2 the
recommended starting point is 300Ω, while unity gain
applications should try 400Ω.
FIGURE 2A. TOP LAYOUT
PC Board Layout
The frequency performance of this amplifier depends a great
deal on the amount of care taken in designing the PC board.
The use of low inductance components such as chip
resistors and chip capacitors is strongly recommended,
while a solid ground plane is a must!
Attention should be given to decoupling the power supplies.
A large value (10µF) tantalum in parallel with a small value
chip (0.1µF) capacitor works well in most cases.
Terminated microstrip signal lines are recommended at the
input and output of the device. Output capacitance, such as
that resulting from an improperly terminated transmission
line will degrade the frequency response of the amplifier and
may cause oscillations. In most cases, the oscillation can be
avoided by placing a resistor in series with the output.
Care must also be taken to minimize the capacitance to
ground seen by the amplifier’s inverting input. The larger this
capacitance, the worse the gain peaking, resulting in pulse
overshoot and possible instability. To this end, it is
recommended that the ground plane be removed under
traces connected to pin 2, and connections to pin 2 should
be kept as short as possible.
An example of a good high frequency layout is the
Evaluation Board shown in Figure 2.
IN
10µF
0.1µF
-5V
GND
FIGURE 2B. BOTTOM LAYOUT
500Ω
500Ω
V
H
8
7
6
5
GND
0.1µF
50Ω
OUT
V
L
10µF
+5V
1
50Ω
2
3
4
FIGURE 2C. SCHEMATIC
FIGURE 2. EVALUATION BOARD SCHEMATIC AND LAYOUT
Evaluation Board
An evaluation board is available for the HS-1135RH,
(HFA11XXEVAL). Please contact your local sales office for
information.
4
FN4099.3
April 6, 2009
HS-1135RH
Burn-In Circuit
HS-1135RH CERDIP
R
2
R
1
R
1
D
2
V-
D
1
C
1
1
2
3
4
8
D
2
V+
C
1
D
1
+
-
7
6
5
NOTES:
1. R
1
= 1kΩ,
±5%
(Per Socket)
2. R
2
= 10kΩ,
±5%
(Per Socket)
3. C
1
= 0.01
µ
F (Per Socket) or 0.1
µ
F (Per Row) Minimum
4. D
1
= 1N4002 or Equivalent (Per Board)
5. D
2
= 1N4002 or Equivalent (Per Socket)
6. V+ = +5.5V
±0.5V
7. V- = -5.5V
±0.5V
Irradiation Circuit
HS-1135RH CERDIP
R
2
R
1
R
1
V-
C
2
1
2
3
4
8
+
-
7
6
5
C
1
V+
NOTES:
8. R
1
= 1kΩ,
±5%
9. R
2
= 10kΩ,
±5%
10. C
1
= C
2
= 0.01
µ
F
11. V+ = +5.0V
±0.5V
12. V- = -5.0V
±0.5V
5
FN4099.3
April 6, 2009
嵌入式系统
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